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NCP1729 Switched Capacitor Voltage Inverter
The NCP1729 is a CMOS charge pump voltage inverter that is designed for operation over an input voltage range of 1.15 V to 5.5 V with an output current capability in excess of 50 mA. The operating current consumption is only 122 mA, and a power saving shutdown input is provided to further reduce the current to a mere 0.4 mA. The device contains a 35 kHz oscillator that drives four low resistance MOSFET switches, yielding a low output resistance of 26 W and a voltage conversion efficiency of 99%. This device requires only two external 3.3 mF capacitors for a complete inverter making it an ideal solution for numerous battery powered and board level applications. The NCP1729 is available in the space saving TSOP-6 package.
Features http://onsemi.com MARKING DIAGRAM
1 TSOP-6 (SOT23-6) SN SUFFIX CASE 318G 6 EADAYW G G 1
* * * * * * * * * * * * * * * *
Operating Voltage Range of 1.15 V to 5.5 V Output Current Capability in Excess of 50 mA Low Current Consumption of 122 mA Power Saving Shutdown Input for a Reduced Current of 0.4 mA Operation at 35 kHz Low Output Resistance of 26 W Space Saving TSOP-6 Package Pb-Free Package is Available
EAD A Y W G
= Device Code = Assembly Location = Year = Work Week = Pb-Free Package
(Note: Microdot may be in either location)
PIN CONNECTIONS
Vout Vin C- 1 2 3 (Top View) 6 5 4 C+ SHDN GND
Typical Applications
LCD Panel Bias Cellular Telephones Pagers Personal Digital Assistants Electronic Games Digital Cameras Camcorders Hand Held Instruments
ORDERING INFORMATION
Device NCP1729SN35T1 Package TSOP-6 Shipping 3000 / Tape & Reel 3000 / Tape & Reel
-Vout 1 Vin 2 3 6
NCP1729SN35T1G
TSOP-6 (Pb-Free)
5 4
For information on tape and reel specifications, including part orientation and tape sizes, please refer to our Tape and Reel Packaging Specifications Brochure, BRD8011/D.
This device contains 77 active transistors.
Figure 1. Typical Application
(c) Semiconductor Components Industries, LLC, 2006
1
March, 2006 - Rev. 4
Publication Order Number: NCP1729/D
NCP1729
MAXIMUM RATINGS*
Rating Input Voltage Range (Vin to GND) Symbol Vin Value -0.3 to 6.0 -6.0 to 0.3 100 Unit V V
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Output Voltage Range (Vout to GND) Output Current Vout Iout mA Output Short Circuit Duration (Vout to GND) Operating Junction Temperature tSC TJ Indefinite 150 256 313 sec C Power Dissipation and Thermal Characteristics Thermal Resistance, Junction-to-Air Maximum Power Dissipation @ TA = 70C Storage Temperature RqJA PD Tstg C/W mW C -55 to 150 Stresses exceeding Maximum Ratings may damage the device. Maximum Ratings are stress ratings only. Functional operation above the Recommended Operating Conditions is not implied. Extended exposure to stresses above the Recommended Operating Conditions may affect device reliability. *ESD Ratings ESD Machine Model Protection up to 200 V, Class B ESD Human Body Model Protection up to 2000 V, Class 2
ELECTRICAL CHARACTERISTICS (Vin = 5.0 V, C1 = 3.3 mF, C2 = 3.3 mF, TA = -40C to 85C, typical values shown are for TA = 25C unless otherwise noted. See Figure 14 for Test Setup.)
Characteristic Operating Supply Voltage Range (SHDN = Vin, RL = 10 k) Supply Current Device Operating (SHDN = 5.0 V, RL = R) TA = 25C TA = 85C Supply Current Device Shutdown (SHDN = 0 V) TA = 25C TA = 85C Oscillator Frequency TA = 25C TA = -40C to 85C Output Resistance (Iout = 25 mA, Note 1) Voltage Conversion Efficiency (RL = R) Power Conversion Efficiency (RL = 1.0 k) Shutdown Input Threshold Voltage (Vin = 1.5 V to 5.5 V) High State, Device Operating Low State, Device Shutdown Shutdown Input Bias Current High State, Device Operating, SHDN = 5.0 V TA = 25C TA = 85C Low State, Device Shutdown, SHDN = 0 V TA = 25C TA = 85C Wake-Up Time from Shutdown (RL = 1.0 k) Symbol Vin Iin - - ISHDN - - fOSC 24.5 19 Rout VEFF PEFF Vth(SHDN) - - IIH - - IIL - - tWKUP - 5.0 100 1.0 - - - ms 5.0 100 - - 0.6 Vin 0.5 Vin - - pA - 99 - 33.5 - 26 99.9 96 45.6 54 50 - - W % % V 0.4 1.7 - - kHz 122 128 200 200 mA Min 1.5 to 5.5 Typ 1.15 to 6.0 Max - Unit V mA
1. Capacitors C1 and C2 contribution is approximately 20% of the total output resistance.
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100 Rout, OUTPUT RESISTANCE (W) 90 80 70 60 50 40 30 20 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0 5.5 Rout, OUTPUT RESISTANCE (W) Figure 14 Test Setup TA = 25C 100 90 80 70 60 50 40 30 20 -50 -25 0 25 50 75 100 Vin = 5.0 V Vin = 3.3 V Figure 14 Test Setup Vin = 1.5 V Vin = 2.0 V
Vin, SUPPLY VOLTAGE (V)
TA, AMBIENT TEMPERATURE (C)
Figure 2. Output Resistance vs. Supply Voltage
Figure 3. Output Resistance vs. Ambient Temperature
35 Iout, OUTPUT CURRENT (mA) 30 25 20 15 10 5 0 0 10 20 Vin = 1.90 V Vout = -1.50 V Figure 14 Test Setup TA = 25C 30 40 50 Vin = 3.15 V Vout = -2.50 V Vin = 4.75 V Vout = -4.00 V
Vout, OUTPUT VOLTAGE RIPPLE (mVp-p)
350 300 250 200 150 100 50 0 0 10 20 30 40 50 C1, C2, C3, CAPACITANCE (mF) Vin = 3.15 V Vout = -2.50 V Vin = 1.90 V Vout = -1.50 V Vin = 4.75 V Vout = -4.00 V Figure 14 Test Setup TA = 25C
C1, C2, C3, CAPACITANCE (mF)
Figure 4. Output Current vs. Capacitance
Figure 5. Output Voltage Ripple vs. Capacitance
39 Figure 14 Test Setup 38 Vin = 1.5 V 37 36 35 34 33 32 -50 Vin = 5.0 V Vin = 3.3 V
120 Iin, SUPPLY CURRENT (mA) 110 100 90 80 70 60 50 40 1.5
Figure 14 Test Setup RL = TA = 85C
TA = 25C
TA = -40C
2.0
2.5
3.0
3.5
4.0
4.5
5.0
fOSC, OSCILLATOR FREQUENCY (kHz)
130
-25
0
25
50
75
100
Vin, SUPPLY VOLTAGE (V)
TA, AMBIENT TEMPERATURE (C)
Figure 6. Supply Current vs. Supply Voltage
Figure 7. Oscillator Frequency vs. Ambient Temperature
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0.0 Vout, OUTPUT VOLTAGE (V) -1.0 -2.0 -3.0 Vin = 5.0 V -4.0 -5.0 -6.0 0 10 20 30 40 50 Iout, OUTPUT CURRENT (mA) Vin = 2.0 V Figure 14 Test Setup TA = 25C h, POWER CONVERSION EFFICIENCY (%) 100 90 80 70 60 Vin = 1.5 V 50 40 Vin = 2.0 V Vin = 3.3 V Figure 14 Test Setup TA = 25C Vin = 5.0 V
Vin = 3.3 V
0
10
20
30
40
50
Iout, OUTPUT CURRENT (mA)
Figure 8. Output Voltage vs. Output Current
Figure 9. Power Conversion Efficiency vs. Output Current
ISHDN, SHUTDOWN SUPPLY CURRENT (mA)
OUTPUT VOLTAGE RIPPLE AND NOISE = 10 mV / Div. AC COUPLED
Figure 14 Test Setup Vin = 3.3 V Iout = 5.0 mA TA = 25C
1.75 1.50 1.25 Vin = 3.3 V 1.00 0.75 Vin = 1.5 V 0.50 0.25 -50 RL = 10 kW SHDN = GND Vin = 5.0 V
-25
0
25
50
75
100
TIME = 10 ms / Div.
TA, AMBIENT TEMPERATURE (C)
Figure 10. Output Voltage Ripple and Noise
Figure 11. Shutdown Supply Current vs. Ambient Temperature
TA = 25C Vin, SUPPLY VOLTAGE (V) 4.5 4.0 3.5 3.0 2.5 2.0 1.5 0.5 1.0 1.5 2.0 2.5 3.0 Low State, Device Shutdown High State, Device Operating
WAKEUP TIME FROM SHUTDOWN
5.0
SHDN = 5.0V/Div. Vin = 5.0 V RL = 1.0 kW TA = 25C
Vout = 1.0 V/Div.
Vth(SHND), SHUTDOWN INPUT VOLTAGE THRESHOLD (V)
TIME = 400 ms / Div.
Figure 12. Supply Voltage vs. Shutdown Input Voltage Threshold
Figure 13. Wakeup Time From Shutdown
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NCP1729
-Vout RL
Charge Pump Efficiency
1 OSC Vin 2 C3 3
6
C +2
+
5
+ C1
4
C1 = C2 = C3 = 3.3 mF
Figure 14. Test Setup/Voltage Inverter
The overall power conversion efficiency of the charge pump is affected by four factors: 1. Losses from power consumed by the internal oscillator, switch drive, etc. (which vary with input voltage, temperature and oscillator frequency). 2. I2R losses due to the on-resistance of the MOSFET switches on-board the charge pump. 3. Charge pump capacitor losses due to Equivalent Series Resistance (ESR). 4. Losses that occur during charge transfer from the commutation capacitor to the output capacitor when a voltage difference between the two capacitors exists. Most of the conversion losses are due to factors 2, 3 and 4. These losses are given by Equation 1.
P + I out 2 LOSS(2,3,4) 1 (f OSC )C1 ) 8R SWITCH R out ^ I out 2 ) 4ESR C1 ) ESR C2 (eq. 1)
DETAILED OPERATING DESCRIPTION The NCP1729 charge pump converter inverts the voltage applied to the Vin pin. Conversion consists of a two-phase operation (Figure 15). During the first phase, switches S2 and S4 are open and S1 and S3 are closed. During this time, C1 charges to the voltage on Vin and load current is supplied from C2. During the second phase, S2 and S4 are closed, and S1 and S3 are open. This action connects C1 across C2, restoring charge to C2.
S1 Vin C1 S2
The 1/(fOSC)(C1) term in Equation 1 is the effective output resistance of an ideal switched capacitor circuit (Figures 16 and 17). The losses due to charge transfer above are also shown in Equation 2. The output voltage ripple is given by Equation 3.
PLOSS + [ 0.5C 1 (Vin 2 * Vout 2) ) 0.5C2 (VRIPPLE 2 * 2VoutVRIPPLE)] fOSC (eq. 2)
C2
V
S3 S4 -Vout From OSC Vin
RIPPLE
+
Iout (f )(C ) OSC 2
) 2(I out)(ESR ) C2
(eq. 3)
f Vout RL
Figure 15. Ideal Switched Capacitor Charge Pump
C1
C2
APPLICATIONS INFORMATION
Output Voltage Considerations Figure 16. Ideal Switched Capacitor Model
The NCP1729 performs voltage conversion but does not provide regulation. The output voltage will drop in a linear manner with respect to load current. The value of this equivalent output resistance is approximately 26 W nominal at 25C with Vin = 5.0 V. Vout is approximately -5.0 V at light loads, and drops according to the equation below:
VDROP + Iout Rout Vout + * (Vin * VDROP)
REQUIV Vin R + 1 C1 RL Vout
EQUIV
f
C2
Figure 17. Equivalent Output Resistance
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Capacitor Selection
In order to maintain the lowest output resistance and output ripple voltage, it is recommended that low ESR capacitors be used. Additionally, larger values of C1 will lower the output resistance and larger values of C2 will reduce output voltage ripple. (See Equation 3). Table 1 shows various values of C1, C2 and C3 with the corresponding output resistance values at 25C. Table 2 shows the output voltage ripple for various values of C1, C2 and C3. The data in Tables 1 and 2 was measured not calculated.
Table 1. Output Resistance vs. Capacitance (C1 = C2 = C3), Vin = 4.75 V and Vout = -4.0 V
C1 = C2 = C3 (mF) 0.68 1.3 3.3 7.3 10 24 50 Rout (W) 55.4 36.9 26.0 25.8 25.5 25.0 24.0
Vout to GND, it is recommended that a large value capacitor (at least equal to C1) be connected from Vin to GND. If the device is loaded from Vin to Vout, a small (0.7 mF) capacitor between the pins is sufficient.
Voltage Inverter
The most common application for a charge pump is the voltage inverter (Figure 14). This application uses two or three external capacitors. The C1 (pump capacitor) and C2 (output capacitor) are required. The input bypass capacitor C3, may be necessary depending on the application. The output is equal to -Vin plus any voltage drops due to loading. Refer to Tables 1 and 2 for capacitor selection. The test setup used for the majority of the characterization is shown in Figure 14.
Layout Considerations
As with any switching power supply circuit, good layout practice is recommended. Mount components as close together as possible to minimize stray inductance and capacitance. Also use a large ground plane to minimize noise leakage into other circuitry.
Capacitor Resources
Table 2. Output Voltage Ripple vs. Capacitance (C1 = C2 = C3), Vin = 4.75 V and Vout = -4.0 V
C1 = C2 = C3 (mF) 0.68 1.3 3.3 7.3 10 24 50 Output Voltage Ripple (mV) 322 205 120 69 56 32 20
Selecting the proper type of capacitor can reduce switching loss. Low ESR capacitors are recommended. The NCP1729 was characterized using the capacitors listed in Table 3. This list identifies low ESR capacitors for the voltage inverter application.
Table 3. Capacitor Types
Manufacturer/Contact AVX 843-448-9411 www.avxcorp.com Cornell Dubilier 508-996-8561 www.cornell-dubilier.com Sanyo/Os-con 619-661-6835 www.sanyovideo.com/oscon.htm Vishay 603-224-1961 www.vishay.com Part Types/Series TPS
ESRD
SN SVP 593D 594
Input Supply Bypassing
The input voltage, Vin should be capacitively bypassed to reduce AC impedance and minimize noise effects due to the switching internals in the device. If the device is loaded from
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NCP1729
-Vout + Vin +
1 OSC 2
6
5 +
3
4
Capacitors = 3.3 mF
Figure 18. Voltage Inverter
The NCP1729 primary function is a voltage inverter. The device will convert 5.0 V into -5.0 V with light loads. Two capacitors are required for the inverter to function. A third capacitor, the input bypass capacitor, may be required depending on the power source for the inverter. The performance for this device is illustrated below.
0 TA = 25C Vout, OUTPUT VOLTAGE (V) -1.0 -2.0 -3.0 -4.0 -5.0 -6.0 0 10 20 30 40 50 Iout, OUTPUT CURRENT (mA) Vin = 3.3 V Vin = 5.0 V
Figure 19. Voltage Inverter Load Regulation, Output Voltage vs. Output Current
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Vin 6 OSC 2 5 + 3 4 3 4 + 2 -Vout 6 OSC 5 +
1 + +
1
Capacitors = 3.3 mF
Figure 20. Cascaded Devices for Increased Negative Output Voltage
Two or more devices can be cascaded for increased output voltage. Under light load conditions, the output voltage is approximately equal to -Vin times the number of stages. The converter output resistance increases dramatically with each additional stage. This is due to a reduction of input voltage to each successive stage as the converter output is loaded. Note that the ground connection for each successive stage must connect to the negative output of the previous stage. The performance characteristics for a converter consisting of two cascaded devices are shown below.
-1.0 -2.0 Vout, OUTPUT VOLTAGE (V) -3.0 -4.0 -5.0 -6.0 -7.0 -8.0 -9.0 -10.0 0 10 20 TA = 25C 30 40 A Curve A B Vin (V) 5.0 3.0 Rout (W) 145 180 B
Iout, OUTPUT CURRENT (mA)
Figure 21. Cascade Load Regulation, Output Voltage vs. Output Current
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NCP1729
1 OSC Vin
6
-Vout + 2 5 + + 3 4 + +
Capacitors = 3.3 mF
Figure 22. Negative Output Voltage Doubler
A single device can be used to construct a negative voltage doubler. The output voltage is approximately equal to -2.0 Vin minus the forward voltage drop of each external diode. The performance characteristics for the above converter are shown below. Note that curves A and C show the circuit performance with economical 1N4148 diodes, while curves B and D are with lower loss MBRA120E Schottky diodes.
0 Vout, OUTPUT VOLTAGE (V) TA = 25C -2.0 A -4.0 B -6.0 C Curve A B C D D -10.0 0 10 20 30 40 Iout, OUTPUT CURRENT (mA) 5.0 MBRA120E 85 Vin (V) 3.0 3.0 5.0 All Diodes 1N4148 MBRA120E 1N4148 Rout (W) 118 107 91
-8.0
Figure 23. Doubler Load Regulation, Output Voltage vs. Output Current
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NCP1729
1 OSC Vin
6
-Vout + 2 5 + + 3 4 + + + +
Capacitors = 3.3 mF
Figure 24. Negative Output Voltage Tripler
A single device can be used to construct a negative voltage tripler. The output voltage is approximately equal to -3.0 Vin minus the forward voltage drop of each external diode. The performance characteristics for the above converter are shown below. Note that curves A and C show the circuit performance with economical 1N4148 diodes, while curves B and D are with lower loss MBRA120E Schottky diodes.
0 -2.0 Vout, OUTPUT VOLTAGE -4.0 -6.0 -8.0 -10.0 -12.0 -14.0 -16.0 0 10 20 30 40 50 Iout, OUTPUT CURRENT TA = 25C D B C Curve A B C D Vin (V) 3.0 3.0 5.0 5.0 All Diodes 1N4148 MBRA120E 1N4148 MBRA120E Rout (W) 247 228 198 188 A
Figure 25. Tripler Load Regulation, Output Voltage vs. Output Current
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1 OSC
6 +
Vin
+
2
5
+
Vout
3
4
Capacitors = 3.3 mF
Figure 26. Positive Output Voltage Doubler
A single device can be used to construct a positive voltage doubler. The output voltage is approximately equal to 2.0 Vin minus the forward voltage drop of each external diode. The performance characteristics for the above converter are shown below. Note that curves A and C show the circuit performance with economical 1N4148 diodes, while curves B and D are with lower loss MBRA120E Schottky diodes.
10.0 D Vout, OUTPUT VOLTAGE (V) 8.0 C 6.0 Curve B A 4.0 A 2.0 TA = 25C 0 0 10 20 30 40 Iout, OUTPUT CURRENT (mA) B C D Vin (V) 3.0 3.0 5.0 5.0 All Diodes 1N4148 MBRA120E 1N4148 MBRA120E Rout (W) 32 25 24 19.3
Figure 27. Doubler Load Regulation, Output Voltage vs. Output Current
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1 OSC
6 + + Vout + +
Vin
+
2
5
3
4
Capacitors = 3.3 mF
Figure 28. Positive Output Voltage Tripler
A single device can be used to construct a positive voltage tripler. The output voltage is approximately equal to 3.0 Vin minus the forward voltage drop of each external diode. The performance characteristics for the above converter are shown below. Note that curves A and C show the circuit performance with economical 1N4148 diodes, while curves B and D are with lower loss MBRA120E Schottky diodes.
14.0 D Vout, OUTPUT VOLTAGE (V) 12.0 10.0 C 8.0 B 6.0 B 4.0 A 2.0 TA = 25C 0 0 10 20 30 40 50 Iout, OUTPUT CURRENT (mA) D 5.0 MBRA120E 78 C 5.0 1N4148 88 3.0 MBRA120E 95 A 3.0 1N4148 110 Curve Vin (V) All Diodes Rout (W)
Figure 29. Tripler Load Regulation, Output Voltage vs. Output Current
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-Vout + 1 OSC Vin 2 5 100 k 3 4 6
+
+
Capacitors = 3.3 mF
Figure 30. Load Regulated Negative Output Voltage
A zener diode can be used with the shutdown input to provide closed loop regulation performance. This significantly reduces the converter's output resistance and dramatically enhances the load regulation. For closed loop operation, the desired regulated output voltage must be lower in magnitude than -Vin. The output will regulate at a level of -VZ + Vth(SHDN). Note that the shutdown input voltage threshold is typically 0.5 Vin and therefore, the regulated output voltage will change proportional to the converter's input. This characteristic will not present a problem when used in applications with constant input voltage. In this case the zener breakdown was measured at 25 mA. The performance characteristics for the above converter are shown below. Note that the dashed curve sections represent the converter's open loop performance.
-1.0 TA = 25C Vout, OUTPUT VOLTAGE (V) -2.0 A
-3.0
B Curve Vin (V) 3.3 5.0 Vz (V) 3.9 6.5 Vout (V) -2.1 -3.8
-4.0
A B
-5.0 0 10 20 30 40 50 60 70 Iout, OUTPUT CURRENT (mA)
Figure 31. Load Regulation, Output Voltage vs. Output Current
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-Vout 1 OSC Vin 2 5 R2 6 R1 +
+
+
3
4
10 k Capacitors = 3.3 mF
Figure 32. Line and Load Regulated Negative Output Voltage
An adjustable shunt regulator can be used with the shutdown input to give excellent closed loop regulation performance. The shunt regulator acts as a comparator with a precise input offset voltage which significantly reduces the converter's output resistance and dramatically enhances the line and load regulation. For closed loop operation, the desired regulated output voltage must be lower in magnitude than -Vin. The output will regulate at a level of -Vref (R2/R1 + 1). The adjustable shunt regulator can be from either the TLV431 or TL431 families. The comparator offset or reference voltage is 1.25 V or 2.5 V respectively. The performance characteristics for the converter are shown below. Note that the dashed curve sections represent the converter's open loop performance.
TA = 25C -1.0 Vout, OUTPUT VOLTAGE (V) A -2.0 Vout, OUTPUT VOLTAGE (V) -1.5 -0.5 Iout = 25 mA R1 = 10 k R2 = 24 k TA = 25C
-2.5
-3.0
B
-4.0
-3.5
-5.0
0
10
20
30
40
50
60
70
-4.5 1.0
2.0
3.0
4.0
5.0
6.0
Iout, OUTPUT CURRENT (mA)
Vin, INPUT VOLTAGE (V)
Figure 33. Load Regulation, Output Voltage vs. Output Current
Figure 34. Line Regulation, Output Voltage vs. Input Current
Curve A B
Vin (V) 3.0 5.0
R1 (W) 10 k 10 k
R2 (W) 5.0 k 24 k
Vout (V) -1.8 -4.2
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-Vout + 1 OSC Vin 2 5 2 6 1 OSC 5 6
+
3
4
3
4
+ Capacitors = 3.3 mF
+
Figure 35. Paralleling Devices for Increased Negative Output Current
An increase in converter output current capability with a reduction in output resistance can be obtained by paralleling two or more devices. The output current capability is approximately equal to the number of devices paralleled. A single shared output capacitor is sufficient for proper operation but each device does require its own pump capacitor. Note that the output ripple frequency will be complex since the oscillators are not synchronized. The output resistance is approximately equal to the output resistance of one device divided by the total number of devices paralleled. The performance characteristics for a converter consisting of two paralleled devices is shown below.
-1.0 Vout, OUTPUT VOLTAGE (V) TA = 25C -2.0 B
-3.0 Curve -4.0 A A B -5.0 0 10 20 30 40 50 60 70 80 90 100 Iout, OUTPUT CURRENT (mA) Vin (V) 5.0 3.0 Rout (W) 14 17
Figure 36. Parallel Load Regulation, Output Voltage vs. Output Current
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Q2 1 OSC Vin 2 C3 3 4 5 6 Q1
C1 + + C2 -Vout
+
C1 = C2 = 470 mF C3 = 220 mF Q1 = PZT751 Q2 = PZT651
-Vout = Vin -VBE(Q1) - VBE(Q2) -2 VF
Figure 37. External Switch for Increased Negative Output Current
The output current capability of the NCP1729 can be extended beyond 600 mA with the addition of two external switch transistors and two Schottky diodes. The output voltage is approximately equal to -Vin minus the sum of the base emitter drops of both transistors and the forward voltage of both diodes. The performance characteristics for the converter are shown below. Note that the output resistance is reduced to 1.0 W.
-2.0 Vout, OUTPUT VOLTAGE (V) -2.2 -2.4 -2.6 -2.8 -3.0 -3.2 Vin = 5.0 V Rout = 1.0 W TA = 25C 0 0.1 0.2 0.3 0.4 0.5 0.6
Iout, OUTPUT CURRENT (mA)
Figure 38. Current Boosted Load Regulation, Output Voltage vs. Output Current
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10 k Q2 C1 1 OSC Vin Q1 + C3 3 4 2 5 C1 = C2 = 470 mF C3 = 220 mF Q1 = PZT751 Q2 = PZT651 6 + + C2 R1 -Vout
R2
Figure 39. Line and Load Regulated Negative Output Voltage with High Current Capability
This converter is a combination of Figures 37 and 32. It provides a line and load regulated output of -2.47 V at up to 300 mA with an input voltage of 5.0 V. The output will regulate at a level of -Vref (R2/R1 + 1). The performance characteristics are shown below. Note that the dashed line is the open loop and the solid line is the closed loop configuration for the load regulation.
-2.0 Vout, OUTPUT VOLTAGE (V) -2.2 -2.4 -2.6 -2.8 -3.0 -3.2 Vout, OUTPUT VOLTAGE (V) -0.1 Iout = 100 mA R1 = R2 = 10 kW TA = 25C
-0.6
-1.1
-1.6
Vin = 5.0 V Rout = 1.0 W R1 = R2 = 10 kW TA = 25C 0 0.1 0.2 0.3 0.4 0.5 0.6
-2.1
-2.6 2.5
3.0
3.5
4.0
4.5
5.0
5.5
Iout, OUTPUT CURRENT (A)
Vin, INPUT VOLTAGE (V)
Figure 40. Current Boosted Load Regulation, Output Voltage vs. Output Current
Figure 41. Current Boosted Line Regulation, Output Voltage vs. Output Current
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NCP1729
50 Q2 1 OSC Vin 2 C3 3 4 Capacitors = 220 mF Q1 = PZT751 Q2 = PZT651 5 6 50 Q1 + + + C2 C1 Vout
Figure 42. Positive Output Voltage Doubler with High Current Capability
The NCP1729 can be configured to produce a positive output voltage doubler with current capability of 500 mA. This is accomplished with the addition of two external switch transistors and two Schottky diodes. The output voltage is approximately equal to 2.0 Vin minus the sum of the base emitter drops of both transistors and the forward voltage of both diodes. The performance characteristics for the converter is shown below. Note that the output resistance is reduced to 1.8 W.
8.8 Vout, OUTPUT VOLTAGE (V) Vin = 5.0 V Rout = 1.8 W TA = 25C
8.4
8.0
7.6
7.2
0
0.1
0.2
0.3
0.4
0.5
Iout, OUTPUT CURRENT (mA)
Figure 43. Positive Doubler with Current Boosted Load Regulation, Output Voltage vs. Output Current
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NCP1729
R1 10 k 50 Q2 1 OSC Vin 2 C3 3 4 5 Capacitors = 220 mF Q1 = PZT751 Q2 = PZT651 6 50 Q1 + C1 + + C2 R2 Vout
Figure 44. Line and Load Regulated Positive Output Voltage Doubler with High Current Capability
This converter is a combination of Figures 42 and the shunt regulator to close the loop. In this case the anode of the regulator is connected to ground. It provides a line and load regulated output of 7.6 V at up to 300 mA with a input voltage of 5.0 V. The output will regulate at a level of Vref (R2/R1 + 1). The open loop configuration is the dashed line and the closed loop is the solid line. The performance characteristics are shown below.
8.8 Vout, OUTPUT VOLTAGE (V) Vout, OUTPUT VOLTAGE (V) 8.6 8.4 8.2 8.0 7.8 7.6 7.4 7.2 0 0.1 0.2 0.3 0.4 0.5 0.6 Vin = 5.0 V Rout = 1.8 W Open Loop Rout = 0.5 W Closed Loop R1 = 10 k R2 = 51.3 kW TA = 25C 8.0 7.0 6.0 5.0 4.0 3.0 2.0 1.0 1.0 Iout = 100 mA R1 = 10 k R2 = 51.3 kW TA = 25C 2.0 3.0 4.0 5.0 6.0
Iout, OUTPUT CURRENT (A)
Vin, INPUT VOLTAGE (V)
Figure 45. Current Boosted Close Loop Load Regulation, Output Voltage vs. Output Current
Figure 46. Current Boosted Close Loop Line Regulation, Output Voltage vs. Input Voltage
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NCP1729
Vin = -5.0 V 6 OSC 2 5 + C + C
1 + C
3
4 + Capacitors = 3.3 mF C
Vout = -2.5 V
Figure 47. Negative Input Voltage Splitter
A single device can be used to split a negative input voltage. The output voltage is approximately equal to -Vin / 2.0. The performance characteristics are shown below. Note that the converter has an output resistance of 10 W.
-1.5 Vout, OUTPUT VOLTAGE (V)
-1.7
-1.9
-2.1
-2.3
Rout = 10 W TA = 25C 0 10 20 30 40 50 60 70 80
-2.5 Iout, OUTPUT CURRENT (mA)
Figure 48. Negative Voltage Splitter Load Regulation, Output Voltage vs. Output Current
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NCP1729
-Vout R1 +
1 OSC Vin 2
6
R2
+
5 10 k +
3
4
+ + +Vout
Capacitors = 10 mF
Figure 49. Combination of a Closed Loop Negative Inverter with a Positive Output Voltage Doubler
All of the previously shown converter circuits have only single outputs. Applications requiring multiple outputs can be constructed by incorporating combinations of the former circuits. The converter shown above combines Figures 26 and 32 to form a regulated negative output inverter with a non-regulated positive output doubler. The magnitude of -Vout is controlled by the resistor values and follows the relationship -Vref (R2/R1 + 1). Since the positive output is not within the feedback loop, its output voltage will increase as the negative output load increases. This cross regulation characteristic is shown in the upper portion of Figure 50. The dashed line is the open loop and the solid line is the closed loop configuration for the load regulation. The load regulation for the positive doubler with a constant load on the -Vout is shown in Figure 51.
9.0 Vout, OUTPUT VOLTAGE (V) Positive Doubler Iout = 15 mA Vout, OUTPUT VOLTAGE (V) 10.0
8.0 -3.0
9.0
Negative Inverter -4.0
Rout = 45 W - Open Loop Rout = 2 W - Closed Loop R1 = 10 k, R2 = 20 k TA = 25C
8.0
Negative Inverter Iout = 15 mA R1 = 10 kW R2 = 20 kW TA = 25C
-5.0 0 10 20 30 Iout, NEGATIVE INVERTER OUTPUT CURRENT (mA)
7.0 0 10 20 30 40 50 Iout, POSITIVE DOUBLER OUTPUT CURRENT (mA)
Figure 50. Load Regulation, Output Voltage vs. Output Current
Figure 51. Load Regulation, Output Voltage vs. Output Current
+ Vin
IC1
C1
C2 -Vout
SHDN
GND
C3 0.5
+
+
GND
Inverter Size = 0.5 in x 0.2 in Area = 0.10 in2, 64.5 mm2
Figure 52. Inverter Circuit Board Layout, Top View Copper Side http://onsemi.com
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NCP1729
PACKAGE DIMENSIONS
TSOP-6 CASE 318G-02 ISSUE M
A L
6 5 1 2 4 3
S
B
NOTES: 1. DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982. 2. CONTROLLING DIMENSION: MILLIMETER. 3. MAXIMUM LEAD THICKNESS INCLUDES LEAD FINISH THICKNESS. MINIMUM LEAD THICKNESS IS THE MINIMUM THICKNESS OF BASE MATERIAL. 4. DIMENSIONS A AND B DO NOT INCLUDE MOLD FLASH, PROTRUSIONS, OR GATE BURRS. MILLIMETERS DIM MIN MAX A 2.90 3.10 B 1.30 1.70 C 0.90 1.10 D 0.25 0.50 G 0.85 1.05 H 0.013 0.100 J 0.10 0.26 K 0.20 0.60 L 1.25 1.55 M 0_ 10 _ S 2.50 3.00 INCHES MIN MAX 0.1142 0.1220 0.0512 0.0669 0.0354 0.0433 0.0098 0.0197 0.0335 0.0413 0.0005 0.0040 0.0040 0.0102 0.0079 0.0236 0.0493 0.0610 0_ 10 _ 0.0985 0.1181
D G M 0.05 (0.002) H C K J
SOLDERING FOOTPRINT*
2.4 0.094
1.9 0.075
0.95 0.037 0.95 0.037
0.7 0.028 1.0 0.039
SCALE 10:1
mm inches
*For additional information on our Pb-Free strategy and soldering details, please download the ON Semiconductor Soldering and Mounting Techniques Reference Manual, SOLDERRM/D.
ON Semiconductor and are registered trademarks of Semiconductor Components Industries, LLC (SCILLC). SCILLC reserves the right to make changes without further notice to any products herein. SCILLC makes no warranty, representation or guarantee regarding the suitability of its products for any particular purpose, nor does SCILLC assume any liability arising out of the application or use of any product or circuit, and specifically disclaims any and all liability, including without limitation special, consequential or incidental damages. "Typical" parameters which may be provided in SCILLC data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. All operating parameters, including "Typicals" must be validated for each customer application by customer's technical experts. SCILLC does not convey any license under its patent rights nor the rights of others. SCILLC products are not designed, intended, or authorized for use as components in systems intended for surgical implant into the body, or other applications intended to support or sustain life, or for any other application in which the failure of the SCILLC product could create a situation where personal injury or death may occur. Should Buyer purchase or use SCILLC products for any such unintended or unauthorized application, Buyer shall indemnify and hold SCILLC and its officers, employees, subsidiaries, affiliates, and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney fees arising out of, directly or indirectly, any claim of personal injury or death associated with such unintended or unauthorized use, even if such claim alleges that SCILLC was negligent regarding the design or manufacture of the part. SCILLC is an Equal Opportunity/Affirmative Action Employer. This literature is subject to all applicable copyright laws and is not for resale in any manner.
PUBLICATION ORDERING INFORMATION
LITERATURE FULFILLMENT: N. American Technical Support: 800-282-9855 Toll Free Literature Distribution Center for ON Semiconductor USA/Canada P.O. Box 61312, Phoenix, Arizona 85082-1312 USA Phone: 480-829-7710 or 800-344-3860 Toll Free USA/Canada Japan: ON Semiconductor, Japan Customer Focus Center 2-9-1 Kamimeguro, Meguro-ku, Tokyo, Japan 153-0051 Fax: 480-829-7709 or 800-344-3867 Toll Free USA/Canada Phone: 81-3-5773-3850 Email: orderlit@onsemi.com ON Semiconductor Website: http://onsemi.com Order Literature: http://www.onsemi.com/litorder For additional information, please contact your local Sales Representative.
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NCP1729/D

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